View MGA-53543_166980.PDF datasheet online --- IC-ON-LINE

Datasheet File OCR Text:

Agilent MGA-53543 50 MHz to 6 GHz High Linear Amplifier
Data Sheet
Features * Lead-free Option Available * Very high linearity at low DC bias power[1] * Low noise figure * Advanced enhancement mode PHEMT technology * Excellent uniformity in product specifications * Low cost surface mount small plastic package SOT-343 (4-lead SC-70) * Tape-and-Reel packaging option available Pin Connections and Package Marking
INPUT 3
Description Agilent Technologies's MGA-53543 is a high dynamic range low noise amplifier MMIC housed in a 4-lead SC-70 (SOT-343) surface mount plastic package. The combination of high linearity, low noise figure and high gain makes the MGA-53543 ideal for cellular/PCS/ W-CDMA base stations, Wireless LAN, WLL and other systems in the 50 MHz to 6 GHz frequency range. MGA-53543 is especially ideal for Cellular/PCS/ W-CDMA basestation applications. With high IP3 and low noise figure, the MGA-53543 may be utilized as a driver amplifier in the transmit chain and as a second stage LNA in the receive chain.
Surface Mount Package SOT-343/4-lead SC70
Specifications 1.9 GHz, 5V, 54 mA (typ) * OIP3: 39 dBm
1 GND
53x
* Noise figure: 1.5 dB * Gain: 15.4 dB * P-1dB: 18.6 dBm Applications * Base station radio card * High linearity LNA for base stations, WLL, WLAN, and other applications in the 50 MHz to 6 GHz range
GND
4
2
OUTPUT & Vd
Note: Top View. Package marking provides orientation and identification. "53" = Device Code "x" = Date code character identifies month of manufacture.
Attention: Observe precautions for handling electrostatic sensitive devices.
ESD Machine Model (Class A) ESD Human Body Model (Class 1A)
Simplified Schematic
Note: 1. The MGA-53543 has a superior LFOM of 15 dB. Linearity Figure of Merit (LFOM) is essentially OIP3 divided by DC bias power. There are few devices in the market that can match its combination of high linearity and low noise figure at the low DC bias power of 5V/54 mA.
bias
Refer to Agilent Application Note A004R: Electrostatic Discharge Damage and Control.
MGA-53543 Absolute Maximum Ratings [1] Symbol
Vin Vd Pd Pin jc Tj TSTG
Parameter
Maximum Input Voltage Supply Voltage Power Dissipation [2] CW RF Input Power Thermal Resistance [3] Junction Temperature Storage Temperature
Units
V V mW dBm C/W C C
Absolute Maximum
0.8 5.5 400 13 130 150 -65 to 150 Notes: 1. Operation of this device in excess of any of these limits may cause permanent damage. 2. Source lead temperature is 25C. Derate 7.7mW/C for TL > 98C 3. Thermal resistance measured using 150C Liquid Crystal Measurement Technique.
Electrical Specifications Tc = +25C, Zo = 50 , Vd = 5V, unless noted Symbol
Id NF [1]
Parameter and Test Condition
Current Drawn Noise Figure
Frequency
N/A 2.4 GHz 1.9 GHz 0.9 GHz 2.4 GHz 1.9 GHz 0.9 GHz 2.4 GHz 1.9 GHz 0.9 GHz 2.4 GHz 1.9 GHz 0.9 GHz 1.9 GHz 0.9 GHz 2.4 GHz 1.9 GHz 0.9 GHz 2.4 GHz 1.9 GHz 0.9 GHz 1.9 GHz 0.9 GHz
Units
mA dB
Min.
40
Typ.
54 1.9 1.5 1.3
Max.
70 1.9
[3]
2.7 0.06
Gain [1]
Gain
dB
14
15.1 15.4 17.4 38.7 39.1 39.7 18.3 18.6 19.3 29.7 28.3 -12.7 -13.2 -11.1 -25.1 -14.3 -14.4 -23.4 -22.3
17.0
0.25
OIP3 [1,2]
Output Third Order Intercept Point
dBm
36
1.89
P1dB [1]
Output Power at 1 dB Gain Compression
dBm % % dB
PAE [1] RLin[1]
Power Added Effciency at P1dB Input Return Loss
RLout [1]
Output Return Loss
dB dB
ISOL [1]
Isolation |s12|2
Notes: 1. Measurements obtained from a test circuit described in Figure 1. Input and output tuners tuned for maximum OIP3 while keeping VSWR better than 2:1. Data corrected for board losses. 2. I) Output power level and frequency of two fundamental tones at 1.9 GHz: F1 = 5.49 dBm, F2 = 5.49 dBm, F1 = 1.905 GHz, and F2 = 1.915 GHz. II) Output power level and frequency of two fundamental tones at 900 MHz: F1 = -0.38 dBm, F2 = -0.38 dBm, F1 = 905 MHz, and F2 = 915 MHz. 3. Standard deviation data are based on at least 500 pieces sample size taken from 8 wafer lots. Future wafers allocated to this product may have nominal values anywhere between the upper and lower spec limits.
RF Input
Input Gamma & Transmission Line Source = 0.38 156 (0.7 dBm Loss)
Vd
Output Gamma & Transmission Line with Bias Tee Load = 0.05 45 (0.85 dBm Loss)
Figure 1. Block Diagram of 1.9 GHz Test Fixture.
53x
RF Output
2
MGA-53543 Typical Performance All data measured at Tc = 25C, Vd = 5 V with input and output tuners tuned for maximum OIP3 while keeping VSWR better than 2:1 unless stated otherwise.
45
-40C +25C +85C
45
24
-40C +25C +85C
40
OIP3 (dBm)
40
P1dB (dBm) OIP3 (dBm)
20
35
35
16
30
30
12 25 25
20 0 1 2 3 4 5 6 7 FREQUENCY (GHz)
20 -5 -1 3 7 11 15 Pout (dBm)
8 0 1 2 3 4 5 6 7 FREQUENCY (GHz)
Figure 2. Output Third Order Intercept Point vs. Frequency and Temperature.
20
-40C +25C +85C
Figure 3. Output Third Order Intercept Point vs. Output Power at 2 GHz.
3.8
Figure 4. Output Power at 1dB Compression vs. Frequency and Temperature.
0
-5
S11 & S22 (dB)
|S21|2 (dB)
15
Fmin (dB)
2.8
-10
-15
S22 S11
10
1.8
-40C +25C +85C
-20
5 0 1 2 3 4 5 6 FREQUENCY (GHz)
0.8 0 1 2 3 4 5 6 FREQUENCY (GHz)
-25 0 1 2 3 4 5 6 FREQUENCY (GHz)
Figure 5. |S21|2 vs. Frequency and Temperature.
-19
Figure 6. Fmin vs. Frequency and Temperature.
70 60
Figure 7. S11 and S22 (50) vs. Frequency.
-21
S12
ISOLATION (dB)
50
Id (mA)
-23
40 30 20
-25
-27 10 -29 0 1 2 3 4 5 6 FREQUENCY (GHz) 0 0 1 2 3 Vd (V) 4
-40C +25C +85C
5
6
Figure 8. Isolation vs. Frequency.
Figure 9. Current vs. Voltage and Temperature.
3
MGA-53543 Typical Scattering Parameters TC = 25C, Vd = 5.0V, Id = 54 mA, ZO = 50 , (in ICM test fixture) Freq (GHz)
0.05 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0 6.5 7.0 7.5 8.0 8.5 9.0 9.5 10.0
S11 Mag.
0.823 0.641 0.439 0.349 0.305 0.251 0.233 0.22 0.212 0.207 0.201 0.198 0.196 0.194 0.195 0.197 0.199 0.201 0.205 0.212 0.216 0.221 0.229 0.235 0.241 0.25 0.293 0.342 0.394 0.445 0.497 0.534 0.565 0.595 0.615 0.635 0.662 0.682 0.715 0.752 0.754
S11 Ang.
-38.8 -66.7 -98.7 -116.8 -128.9 -135.6 -142.5 -147.5 -151.1 -153.6 -155.3 -157.3 -158.2 -158.4 -159.4 -160 -160.1 -160.5 -161.5 -162.6 -163.1 -164.8 -166.1 -167.2 -169.2 -171.4 176.8 162.2 148.2 133.9 121.6 109.9 99.5 88.2 77.5 65.2 53.9 43.4 32.3 24.9 16
S21 dB
26.26 24.39 21.55 20.14 19.39 18.92 18.6 18.34 18.12 17.9 17.7 17.51 17.31 17.1 16.9 16.7 16.48 16.26 16.04 15.82 15.59 15.36 15.14 14.9 14.67 14.43 13.28 12.13 10.99 9.84 8.7 7.56 6.46 5.38 4.31 3.3 2.29 1.37 0.45 -0.31 -1.12
S21 Mag.
20.56 16.584 11.954 10.165 9.317 8.826 8.509 8.261 8.053 7.854 7.674 7.505 7.335 7.165 7 6.836 6.666 6.498 6.341 6.179 6.017 5.862 5.714 5.56 5.412 5.265 4.611 4.039 3.544 3.105 2.721 2.388 2.105 1.857 1.643 1.462 1.301 1.171 1.053 0.965 0.879
S21 Ang.
161.3 148.9 142.7 141.8 140.7 139.3 136.7 133.6 130.2 126.7 123 119.2 115.4 111.6 107.7 103.9 100.1 96.3 92.6 88.9 85.3 81.7 78.3 74.7 71.2 67.8 51.5 36.2 21.6 7.8 -5.2 -17.5 -28.8 -39.6 -49.8 -59.6 -68.8 -77.6 -86 -93.5 -101.7
S12 dB
-27.96 -24.29 -22.50 -22.05 -21.94 -21.83 -21.72 -21.72 -21.72 -21.62 -21.62 -21.62 -21.62 -21.62 -21.62 -21.62 -21.72 -21.72 -21.72 -21.83 -21.83 -21.94 -21.94 -22.05 -22.16 -22.16 -22.50 -22.73 -22.62 -22.27 -21.51 -20.72 -19.83 -18.94 -18.27 -17.72 -17.27 -16.77 -16.31 -15.86 -15.55
S12 Mag.
0.04 0.061 0.075 0.079 0.08 0.081 0.082 0.082 0.082 0.083 0.083 0.083 0.083 0.083 0.083 0.083 0.082 0.082 0.082 0.081 0.081 0.08 0.08 0.079 0.078 0.078 0.075 0.073 0.074 0.077 0.084 0.092 0.102 0.113 0.122 0.13 0.137 0.145 0.153 0.161 0.167
S12 Ang.
59.7 40.6 22.9 15.4 11.2 9 7 5.4 4 2.8 1.7 0.7 -0.2 -1.1 -2 -2.8 -3.6 -4.3 -4.9 -5.6 -6.2 -6.7 -7.3 -7.6 -7.9 -8.2 -8.6 -7.3 -5.3 -3.4 -2.7 -3.5 -5.9 -10.4 -16 -22.1 -28.2 -34.2 -40.9 -47.5 -55.3
S22 Mag.
0.72 0.558 0.344 0.235 0.176 0.097 0.087 0.094 0.11 0.129 0.148 0.169 0.186 0.203 0.219 0.235 0.248 0.261 0.273 0.283 0.293 0.301 0.31 0.316 0.322 0.327 0.338 0.333 0.313 0.287 0.256 0.229 0.204 0.185 0.162 0.127 0.084 0.033 0.028 0.081 0.129
S22 Ang.
-33 -61.5 -95.3 -118.3 -138.2 -167.4 159.7 131.8 110.7 95.4 84.1 74.8 66.6 59.6 53.1 47.6 42.2 37.1 32.4 28 23.8 19.8 16 12.3 8.8 5.5 -9.4 -22.6 -34.9 -48 -62.1 -77.8 -94.1 -108.7 -120.2 -128.8 -132.9 -145.4 57.9 51.3 50.1
K
0.3 0.4 0.7 0.9 0.9 1 1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.2 1.2 1.2 1.2 1.2 1.3 1.3 1.4 1.5 1.6 1.6 1.6 1.6 1.5 1.5 1.5 1.6 1.6 1.6 1.6 1.5 1.6
4
MGA-53543 Typical Noise Parameters TC = 25C, Vd = 5.0V, Id = 54 mA, ZO = 50 , (in ICM test fixture) Freq (GHz)
0.5 0.8 0.9 1.0 1.1 1.5 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 3.0 3.5 3.8 3.9 4.0 4.5 5.0 5.5 5.7 5.8 5.9 6.0 6.5 7.0 7.5 8.0 8.5 9.0 9.5 10.0
Fmin (dB)
1.07 1.11 1.12 1.14 1.14 1.22 1.3 1.31 1.34 1.36 1.35 1.4 1.44 1.49 1.59 1.64 1.71 1.74 1.76 1.96 2.11 2.38 2.49 2.51 2.54 2.61 2.81 3.14 3.48 3.81 4.07 4.16 4.18 4.62
opt Mag
0.108 0.144 0.159 0.171 0.213 0.238 0.223 0.229 0.237 0.243 0.254 0.255 0.264 0.272 0.298 0.369 0.4 0.41 0.417 0.469 0.521 0.555 0.563 0.568 0.583 0.579 0.613 0.63 0.652 0.673 0.694 0.741 0.778 0.771
opt Ang
156.5 173.2 175.3 173.9 166.3 -179 -175.2 -172 -169.3 -167.3 -165 -163.2 -159.9 -158 -142.3 -131.2 -123.8 -123 -120.2 -108 -99.4 -90.1 -87.3 -84.3 -82.7 -81.7 -72.1 -63.1 -52 -42 -32.5 -22.7 -16.7 -8.9
Rn/Zo
0.1 0.09 0.09 0.09 0.08 0.08 0.09 0.09 0.09 0.09 0.09 0.09 0.09 0.1 0.12 0.13 0.16 0.17 0.18 0.26 0.35 0.49 0.56 0.6 0.64 0.66 0.9 1.17 1.56 2.05 2.56 3.21 3.89 4.48
Ga (dB)
19.13 18.28 18.08 17.89 17.71 16.99 16.45 16.27 16.07 15.88 15.69 15.49 15.29 15.09 14.12 13.14 12.56 12.39 12.19 11.23 10.34 9.42 9.04 8.84 8.7 8.52 7.66 6.71 5.78 4.92 4.11 3.47 3.2 2.41
MGA-53543 Typical Linearity Parameters TC = 25C, Vd = 5V, ZO = 50 Freq
500 MHz 900 MHz 1.9 GHz 2.4 GHz
Source[1] Mag
0.31 0.15 0.38 0.49
Source[1] ()
-102 -90 156 177
Load[1] Mag
0.25 0.05 0.05 0.17
Load[1] ()
-13 -165 45 141
OIP3 (dBm)
40 40 39 36
Note: 1. Input and output tuners tuned for maximum OIP3 while keeping VSWR better than 2:1
5
MGA-53543 Applications Information Description The MGA-53543 is a highly linear enhancement mode PHEMT (Pseudomorphic High Electron Mobility Transistor) amplifier with a frequency range extending from 450 MHz to 6 GHz. This range makes the MGA-53543 ideal for both Cellular and PCS basestation applications. With high IP3 and low noise figure, the MGA-53543 may be utilized as a driver amplifier in a transmit chain or as a first or second stage LNA in a receive chain or any other application requiring high linearity. The MGA-53543 operates from a +5 volt power supply and draws a nominal current of 53.8 mA. The RFIC is contained in a miniature SOT-343 (SC-70 4-lead) package to minimize printed circuit board space. This package also offers good thermal dissipation and RF characteristics. Application Guidelines For most applications, all that is required to operate the MGA is to apply a DC bias of +5 volts and match the RF input and output. RF Input The first step to achieve maximum linearity is to match the input of MGA-53543 to one of the linearity values listed on the data sheet. For example, at 1900 MHz the MGA-53543 needs to see a complex impedance of 0.38 156 looking towards the source and an output impedance of 0.05 45 looking towards the load. This may be accomplished by a conjugate match from the system input impedance (typically 50) to S*. Figure 1 shows the location of these input and output Gammas (S and L) required for a high linearity.
S
L
Operating at Other Voltages Operating this RFIC at voltages less than 5V will affect NF, Gain, P1dB and IP3. Figure 3 below demonstrates the affects of changing supply voltage at 1900 MHz.
20
NF, GAIN, and P1dB (dB)
15
Figure 1. Matching for linearity at 1900 MHz.
10
NF Gain P1dB
RF Output Few matching elements are required on the output of the MGA-53543 to achieve good linearity because the output Gamma (L) is close to 50. DC Bias To bias the MGA-53543, a +5 volt supply is connected to the output pin through an inductor, RFC, which isolates the inband signal from the DC supply as shown in Figure 2. Capacitor C3 serves as an RF bypass for inband signals while C4 helps eliminate out of band low frequency signals. An optional resistor R1 may be added to de-Q any resonance created between C3 and C4. Typically values range from 2.2 to 10. A DC blocking capacitor, C2, is used at the output of the MMIC to isolate the supply voltage from succeeding circuits.
C2 RFout RFC
5
0 1 2 3 4 5 SUPPLY VOLTAGE (V)
Figure 3. Gain, NF and P1dB vs. supply voltage at 1900 MHz.
The affects of supply voltage on OIP3 and current at 1900 MHz are shown in Table 1. The MGA-53543 is internally biased for optimal performance at a quiescent current of 53.8 mA. Voltage (V)
1V 2V 3V 4V 5V
OIP3 (dBm)
0 17 28 35 39
Id (mA)
4 16 24 41 51
Table 1. OIP3 vs. supply power.
1
2
53
RFin L1 C4 +5V Figure 2. Schematic diagram with bias connections. C1
3 4
R1
C3
Matching The most important criterion when designing with the MGA-53543 is choosing the input and output-matching network. The MGA-53543 is designed to give excellent IP3 performance, however to achieve this requires both the input and output matching network to present
6
specific impedances (S and L) to the device. It is also possible to match this part for best NF or best gain. However, this will impact the IP3 performance. To achieve best noise figure, the input match will need to be modified to present gamma opt to the device. To achieve the best gain will require both the input and output to be conjugately matched (which will also result in the best return loss). Where needed, the match presented to the input and the output of the device can be modified to compromise between IP3, NF and gain performance. The MGA-53543 has isolation large enough to allows input and output reflection coefficients to be replaced by S11 and S22. In general matching for minimum noise figure does not necessarily guarantee good IP3 performance nor does it guarantee good gain. This is due to the fact that the impedance parameters shown below in Table 2 are not guaranteed to lie near each other on a Smith Chart. So, ideally if all input matching parameters lied near each other or at the same point, and all output parameters also lied near each other or at the same point, the amplifier would have minimum Noise Figure, maximum IP3 and maximum Gain all with a single match. Typically this is not the case and some parameter must be sacrificed to improve another. Table 2 briefly lists the input and output parameters required for each type of match while Figure 4 depicts how each is defined.
Match for
IP3 NF RLin RLout Gain
Input Tuning
s opt S11* none S11*
Output Tuning
L none none S22* S22*
This layout provides ample allowance for package placement by automated assembly equipment without adding parasitics that could impair the high frequency RF performance of the MGA-53543. The layout is shown with a footprint of a SOT-343 package superimposed on the PCB pads for reference. A microstrip layout with sufficient ground vias as shown in Figure 6 is recommended for the MGA-53543 in transitioning from a package pad layout as in Figure 5.
RF OUTPUT
53
Table 2. Required matching for NF, IP3, input & output Return Loss and Gain.
Input Match 50 NF IP3 Gain
53
Output Match 50
opt S
S11*
opt* S*
S11
L*
S22
L
S22*
RF INPUT
Figure 4. Definition of matching parameters.
Figure 6. Microstripline Layout.
PCB Layout A recommended PCB pad layout for the miniature SOT-343 (SC-70) package used by the MGA-53543 is shown in Figure 5.
1.30 0.051 1.00 0.039
0.60 0.024
2.00 0.079
RF Grounding Adequate grounding of Pins 1 and 4 of the RFIC are important to maintain device stability and RF performance. Each of the ground pins should be connected to the ground plane on the backside of the PCB by means of plated through holes (vias). The ground vias should be placed as close to the package terminals as practical to reduce inductance in ground path. It is good practice to use multiple vias to further minimize ground path inductance. PCB Materials FR-4 or G-10 type material is a good choice for most low cost wireless applications using single or multi-layer printed circuit boards. Typical single-layer board thickness is 0.020 to 0.031 inches. Circuit boards thicker than 0.031 inches are not recommended due to excessive inductance in the ground vias.
.090 0.035 1.15 0.045 Dimensions in inches mm
Figure 5. Recommended PCB Pad Layout for Agilent's SC70 4L/SOT-343 Products.
7
For noise figure critical or higher frequency applications, the additional cost of PTFE/glass dielectric materials may be warranted to minimize transmission line loss at the amplifier's input. Application Example The demonstration circuit board for the MGA-53543 is shown in Figure 7. This simple two-layer board contains microstripline on the topside and a solid metal ground plane on the backside with all RF traces having characteristic impedance of 50. Multiple 0.02" vias are used to bring the ground to the topside of the board and help reduce ground inductance. The PCB is fabricated on 0.031" thick Getek(R) GR200D dielectric material with dielectric constant of 4.2.
MGA - 5X
As described earlier, a pure linearity match entails matching only to s and L, thus sacrificing some NF and Gain. This tradeoff is explained below and quantified in Figures 8 and 9. Using the device S-parameters at 1900 MHz, the minimum noise figure possible, whilst matching the input to S, is shown to be 1.7 dB.
S - Optimum linearity match
To accomplish the above performance, a high pass configuration consisting of a 3.3 nH inductor and a 2.2 pF capacitor is used for the input match. Unlike a low pass configuration, a high pass configuration provides not only the impedance transfer required, but also provides excellent stability for the demo board by diminishing low frequency gain. No matching is required for the output, but a good rule of thumb to use when biasing is to limit series reactance to less than 5 and keep shunt reactance above 500. Therefore choosing an RFC of 47 nH, which has a reactance of 561 at 1.9 GHz, helps isolate the DC supply from inband signals. If any high frequency signal is created or enters the DC supply, a 150 pF capacitor is ready to short it to ground. An 8.2 pF capacitor serves primarily as a DC block, but also helps the output match. The completed 1900 MHz amplifier schematic is shown in Figure 10.
8.2 pF RFout 47 nH 150 pF 2.2 3.3 nH +5V 0.1 F
NF = 1.7 dB NF = 1.6 dB NF = 1.5 dB
opt - Optimum NF match
Figure 8. Noise figure performance.
IN OUT
SE
12/01
Vd
Figure 7. MGA-53453 PCB Layout.
1900 MHz HLA Design The following describes a typical application for the MGA-53543 as used in a PCS 1900 MHz band radio receiver optimized for maximum linearity. Steps include matching the input and output as well as providing a DC bias while maintaining acceptable stability, gain and noise figure.
Because gain depends both on the input and output match, the maximum gain is taken from two sets of circles. One is centered around S11 and the other is centered on S22. Thus the maximum attainable gain is the lesser of two circles which completely enclose s or L. For example, in Figure 9 the 16.1 dB input gain circle completely encloses s, but the smallest circle that encloses L is 15.9 dB. Thus the maximum gain is the weakest link or 15.9 dB.
Ga = 15.9 dB Ga = 16.1 dB Ga = 16.2 dB
1
2
53
RFin 2.2 pF
3 4
Figure 10. Schematic for a 1900 MHz stable circuit.
S
S11
L
S22
Ga = 16.2 dB Ga = 16.1 dB
Included with the schematic is a complete RF layout (Figure 15) which includes placement of all components and SMA connectors. A list of part numbers and manufacturer used is given below in Table 3.
Figure 9. Input and output gain circles.
8
3.3 nH 47 nH 2.2 2.2 pF 8.2 pF 150 pF 0.1 F
TOKO LL1608-FS3N3S TOKO LL1005-FH47N RHOM MCR01J2R2 Phycomp 0402CG229C9B200 Phycomp 0402CG829D9B200 Phycomp 0402CG151J9B200 Phycomp 06032F104M8B20
More significant is the linearity delivered by MGA-53543 at 1900 MHz. Figure 13 plots OIP3 over a frequency range from 1850 MHz to1950 MHz. This device produces IIP3 of 24 dBm, OIP3 of 38 dBm and P1dB of 17.8 dBm at 1900 MHz.
45
linearity table on the data sheet. Figure 14 below shows the schematic diagram for a complete 900 MHz circuit using s of 0.15 -90 and L of 0.05 -165 . Table 4 shows the component parts list used. An optional 2.2 resistor at the input helps resistively load the amplifier and improve stability but slightly degrade noise figure.
4.7 pF RFout 15 nH 1000 pF 2.2 22 nH
Table 3. Component parts list for the MGA-53543 HLA at 1900 MHz.
Performance of MGA-53543 at 1900 MHz With a device voltage of +5V, demonstration board MGA-5X delivers a measured noise figure of 1.78 dB and an average gain of 14.5 dB as shown in Figure 11. Gain here is slightly lower than data sheet due to the losses acquired in creating a stable broadband match. Input and output VSWR are both better than 2:1 at 1900 MHz, with input return loss being 10 dB and output return loss at 13 dB.
20
40
OIP3 (dBm)
35
1
2
53
30
RFin
5.6 pF
TX
25 1840 1880 1920
RX
1960 2000
3
4
+5V 2.2
FREQUENCY (MHz)
Figure 13. OIP3 vs. Frequency. Figure 14. Schematic diagram for 900 MHz HLA.
Due to component parasitics and part variations, actual performance may not be identical to this example. 900 MHz HLA Design Optimizing the MGA-53543 for maximum linearity at the Cellular band follows very similar to that of 1900 MHz, except that the input and output tuning conditions will change according to the
22 nH 15 nH 2.2 4.7 pF 5.6 pF 1000 pF
TOKO LL1608-FS22N TOKO LL1005-FS15N RHOM MCR01J2R2 Phycomp 0402CG479C9B200 Phycomp 0402CG569D9B200 Phycomp 04022R102K9B200
15
GAIN and NF (dB)
Gain
10
5 NF 0 1.6
Table 4. Component parts list for the MGA-53543 HLA at 900 MHz.
1.8
2
2.2
2.4
2.6
FREQUENCY (GHz)
Figure 11. Gain and Noise Figure vs Frequency.
0
MGA - 5X
R1 C2 L2 C3 L1 SE 02/01 R2 OUT J2
-5
IN C1
53
RETURN LOSS (dB)
-10
S11
J1
-15 S22 -20
-25 1.6
Vd
1.8
2
2.2
2.4
2.6
FREQUENCY (GHz)
Figure 15. RF Layout for 1900 MHz HLA .
Figure 12. Input and Output return loss vs Frequency.
9
Performance of MGA-53543 at 900 MHz At 900 MHz MGA-53543 delivers OIP3 of 40 dBm along with a noise figure of 1.43 dB. Gain is measured to be 17.1 dB and input return loss is 13.7 dB and output return loss is 13.3 dB as shown in Figures 16 and 17. P1dB is 18.8 dBm.
20 Gain 15
10
5 NF 0 400 600 800 1000 1200 1400
900 MHz LNA Design To demonstrate the versatility of the MGA-53543, the following example describes a cellular band Low Noise Amplifier (LNA) design. The methodology for a 900 MHz LNA design differs from the previous examples in that only the input match affects noise figure. Thus, optimizing for minimum noise figure entails matching only the input to opt instead of S, and the output can either be matched to S22 for better gain or L for better linearity. Figure 18 shows the complete schematic for a 900 MHz low noise amplifier design and Table 5 describes the required components.
4.7 pF
GAIN and NF (dB)
Performance of MGA-53543 at 900 MHz Biased with a +5 Volt supply MGA-53543 delivers a Noise Figure of 1.33 dB at 900 MHz. This number is higher than NFmin only because of loss from lumped element components with parasitic losses. A microstip or distributed element match may improve noise figure by .2 dB. Gain is measured to be 17.4 dB as shown in Figure 19. Input and output VSWR are both better than 2:1, with input return loss of 25 dB and output return loss at 17.5 dB shown in Figure 20.
20 Gain 15
GAIN and NF (dB)
FREQUENCY (MHz)
1 2
RFout 15 nH 1000 pF 2.2
10
Figure 16. Gain and Noise Figure vs Frequency.
53
RFin 4.7 pF 12 nH +5V
3 4
5 NF 0 400 600 800 1000 1200 1400
0
RETURN LOSS (dB)
-5
FREQUENCY (MHz)
Figure 18. Schematic for 900 MHz LNA design.
-10
Figure 19. Gain, Noise Figure and Output Power at 900 MHz.
0 -5
RETURN LOSS (dB)
12 nH
-15 S11 S22 -20 400 600 800 1000 1200 1400
TOKO LL1608-FS12NJ TOKO LL1005-FS15N Phycomp 0402CG479C9B200 RHOM MCR01J2R2 Phycomp 04022R102K9B200
15 nH 4.7 pF 2.2 1000 pF
-10 -15 -20 -25 -30 400 S11 S22 600 800 1000 1200 1400
FREQUENCY (MHz)
Figure 17. Input and Output return loss vs Frequency.
Table 5. Component Parts List for the MGA-53543 HLA at 900 MHz.
FREQUENCY (MHz)
Figure 20. Input and Output return loss at 900 MHz.
Input IIP3 is measured to be 18.6 dBm and P1dB is 19.0 dB at 900 MHz.
10
1900 MHz LNA Design The final example presented in this application note is a PCS band low noise amplifier circuit. As in the 900 MHz LNA example, the input is matched to opt which at 1900 MHz is given as .229 -172 and the output is matched for maximum linearity i.e. L. Biasing the DC supply is done very similar to the 1900 MHz HLA. In fact, the only major difference between the PCS HLA presented earlier and this PCS LNA schematic is a 3.9nH inductor on the input. The complete schematic is shown below.
8.2 pF RFout 47 nH 150 pF
3.9 nH 47 nH 2.2 2.2 pF 8.2 pF 150 pF
TOKO LL1608-FS3N9S TOKO LL1005-FH47N
RETURN LOSS (dB)
0
-5 S22 -10 S11
RHOM MCR01J2R2 Phycomp 0402CG229C9B200 Phycomp 0402CG829D9B200 Phycomp 0402CG151J9B200
-15
Table 6. Component parts list for the MGA-53453 LNA amplifier at 1900 MHz.
-20
-25 1.6
1.8
2.0
2.2
2.4
2.6
1
2
Performance of MGA-53543 at 1900 MHz The typical noise figure for the 1900 MHz LNA is measured to be 1.62 dB with OIP3 at a nominal 37 dBm. Figure 22 shows a measured gain of 14.8 dB and Figure 23 shows the input and output return loss to be 16.4 dB and 11.3 dB respectively. P1dB is 18 dBm.
20
FREQUENCY (GHz)
Figure 23. Input and Output Return Loss for 1900 MHz LNA.
53
RFin 2.2 pF 3.9 nH
3 4
Summary In summary, the MGA-53543 offers very high IP3 as designed, but is versatile enough to give good NF performance wherever needed. Below is a summary of the preceding four examples.
1900 MHz 900 MHz
NF = 1.42 dB OIP3 = 40 dBm Ga = 17.1 dB P1dB = 18.8 dBm NF = 1.33 dB OIP3 = 36 dBm Ga = 17.4 dB P1dB = 19.0 dBm
2.2
GAIN and NF (dB)
+5V
15
Gain
HLA
10
Figure 21. Schematic for 1900 MHz LNA design.
NF = 1.78 dB OIP3 = 38 dBm Ga = 14.5 dB P1dB = 17.8 dBm NF = 1.62 dB OIP3 = 37 dBm Ga = 14.8 dB P1dB = 18.0 dBm
5
Table 6 shows the complete parts list used for the 1900 MHz low noise amplifier.
NF 0 1.6
LNA
2.4 2.6
1.8
2.0
2.2
FREQUENCY (GHz)
Table 7. 1900 MHz and 900 MHz HLA and 1900 MHz and 900 MHz LNA summary.
Figure 22. Gain, Noise Figure vs. Frequency for 1900 MHz LNA.
11
Device Model Refer to Agilent's web site www.agilent.com/view/rf
Part Number Ordering Information
Part Number MGA-53543-TR1 MGA-53543-TR2 MGA-53543-BLK MGA-53543-TR1G MGA-53543-TR2G MGA-53543-BLKG No. of Devices 3000 10000 100 3000 10000 100 Container 7" Reel 13" Reel antistatic bag 7" Reel 13" Reel antistatic bag
Note: For lead-free option, the part number will have the character "G" at the end.
Package Dimensions Outline 43 (SOT-343/SC70 4 lead)
1.30 (.051) BSC
HE
E
1.15 (.045) BSC b1 D
A
A2
b
A1 L DIMENSIONS (mm)
C
SYMBOL E D HE A A2 A1 b b1 c L
MIN. 1.15 1.85 1.80 0.80 0.80 0.00 0.25 0.55 0.10 0.10
MAX. 1.35 2.25 2.40 1.10 1.00 0.10 0.40 0.70 0.20 0.46
NOTES: 1. All dimensions are in mm. 2. Dimensions are inclusive of plating. 3. Dimensions are exclusive of mold flash & metal burr. 4. All specifications comply to EIAJ SC70. 5. Die is facing up for mold and facing down for trim/form, ie: reverse trim/form. 6. Package surface to be mirror finish.
12
Device Orientation
REEL TOP VIEW 4 mm END VIEW
CARRIER TAPE USER FEED DIRECTION COVER TAPE
8 mm
53
53
53
53
(Package marking example orientation shown.)
Tape Dimensions For Outline 4T
P P0 D P2
E
F W C
D1 t1 (CARRIER TAPE THICKNESS) Tt (COVER TAPE THICKNESS)
10 MAX.
K0
10 MAX.
A0
B0
DESCRIPTION CAVITY LENGTH WIDTH DEPTH PITCH BOTTOM HOLE DIAMETER DIAMETER PITCH POSITION WIDTH THICKNESS WIDTH TAPE THICKNESS CAVITY TO PERFORATION (WIDTH DIRECTION) CAVITY TO PERFORATION (LENGTH DIRECTION)
SYMBOL A0 B0 K0 P D1 D P0 E W t1 C Tt F P2
SIZE (mm) 2.40 0.10 2.40 0.10 1.20 0.10 4.00 0.10 1.00 + 0.25 1.55 0.10 4.00 0.10 1.75 0.10 8.00 + 0.30 - 0.10 0.254 0.02 5.40 0.10 0.062 0.001 3.50 0.05 2.00 0.05
SIZE (INCHES) 0.094 0.004 0.094 0.004 0.047 0.004 0.157 0.004 0.039 + 0.010 0.061 + 0.002 0.157 0.004 0.069 0.004 0.315 + 0.012 0.0100 0.0008 0.205 + 0.004 0.0025 0.0004 0.138 0.002 0.079 0.002
PERFORATION
CARRIER TAPE COVER TAPE DISTANCE
13
www.agilent.com/semiconductors
For product information and a complete list of distributors, please go to our web site. For technical assistance call: Americas/Canada: +1 (800) 235-0312 or (916) 788-6763 Europe: +49 (0) 6441 92460 China: 10800 650 0017 Hong Kong: (65) 6756 2394 India, Australia, New Zealand: (65) 6755 1939 Japan: (+81 3) 3335-8152(Domestic/International), or 0120-61-1280(Domestic Only) Korea: (65) 6755 1989 Singapore, Malaysia, Vietnam, Thailand, Philippines, Indonesia: (65) 6755 2044 Taiwan: (65) 6755 1843 Data subject to change. Copyright (c) 2004 Agilent Technologies, Inc. Obsoletes 5988-9628EN November 22, 2004 5989-1804EN

▲Up To Search▲

Price & Availability of MGA-53543

	To Download MGA-53543 Datasheet File
If you can't view the Datasheet, Please click here to try to view without PDF Reader .